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A题/参考/5.md
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# Energetic Echoes: A Multi-Physics ODE-DAE Framework for Smartphone Battery Depletion
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## Summary
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In the modern digital ecosystem, smartphone battery life is a complex dynamic system influenced by the stochasticity of user behavior and the nonlinearity of electrochemical physics. To address the 2026 MCM Problem A, we develop a rigorous, **continuous-time mathematical model** that bridges software-level activities with hardware-level thermodynamics.
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Our approach, the **M**ulti-physics **E**lectro-thermal **S**tability (MES) Framework, integrates three coupled domains:
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1. **Stochastic Load Modeling:** We employ a **Continuous-Time Markov Chain (CTMC)** to model network radio states, explicitly capturing the "energy tail" phenomenon where radios remain active after transmission.
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2. **Electro-Thermal Dynamics:** We utilize a **2RC Thevenin Equivalent Circuit** coupled with a **Dual-Node Bernardi Thermal Model**. This captures the bidirectional feedback where discharge generates heat, and heat modifies internal resistance via Arrhenius dynamics.
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3. **DAE Stability Analysis:** Modeling the Power Management IC (PMIC) as a **Constant Power Load (CPL)**, we formulate the system as a **Differential-Algebraic Equation (DAE)**. We rigorously prove the existence of a unique physical solution and derive a **Saddle-Node Bifurcation** criterion ($\Delta \le 0$) to predict voltage collapse.
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**Keywords:** Differential-Algebraic Equations (DAE), 2RC Thevenin Model, Constant Power Load, Network Tail State, Saddle-Node Bifurcation.
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---
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# 1. Introduction
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## 1.1 Background and Motivation
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Smartphone battery depletion is rarely linear. Users often experience "battery anxiety," where a device shuts down unexpectedly at 15% charge during cold weather or heavy network usage. Traditional Coulomb counting methods fail to explain these phenomena because they ignore voltage polarization, thermal derating, and the negative incremental impedance of modern power regulators.
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## 1.2 Our Approach
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We propose a "mechanisms-first" modeling strategy. Instead of black-box regression, we construct a virtual device governed by physical laws. Our roadmap is defined as follows:
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1. **Power Decomposition:** Decompose user actions into component-level power requests ($P_{\text{req}}$), integrating a stochastic model for network energy.
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2. **Coupled Dynamics:** Link the electrical state (SOC, Voltage) with the thermal state (Core/Surface Temperature).
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3. **System Closure:** Solve the algebraic constraint imposed by the PMIC to determine instantaneous current and stability margins.
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> **[Figure 1 Suggestion: Model Architecture Flowchart]**
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>
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> * **Content:** A block diagram showing data flow. Inputs (Brightness, CPU, Signal) $\to$ Power Model $\to$ DAE Solver $\to$ Battery Physics (Electrical + Thermal).
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> * **Why:** Demonstrates the closed-loop nature of the model.
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---
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# 2. Assumptions and Notations
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## 2.1 Modeling Assumptions
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To ensure the model is physically interpretable and mathematically tractable, we make the following foundational assumptions:
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1. **Mechanism-First Principle:** State of Charge (SOC), voltage polarization, and temperature evolution are described by physical differential equations. Data is used strictly for parameter identification.
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2. **2RC Thevenin Equivalence:** The battery's electrochemical dynamics are approximated by a second-order RC equivalent circuit, capturing fast and slow polarization time constants.
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3. **Constant Power Load (CPL) Approximation:** The PMIC regulation bandwidth far exceeds electrochemical time constants. Thus, on the battery dynamics timescale, $V(t)I(t) = P_{\text{batt}}(t)$. We explicitly address the stability issues arising from CPL's negative incremental impedance in Section 4.7.
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4. **Bernardi Energy Balance:** Heat generation follows the Bernardi framework. We strictly avoid double-counting external device power as internal battery heat.
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5. **Network Tail State CTMC:** Radio states (Idle, Active, Tail) are modeled as a Continuous-Time Markov Chain to capture the energy consumption of RRC state transitions.
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6. **Quasi-Static Aging:** For a single discharge cycle, State of Health (SOH) is approximated as constant.
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## 2.2 Nomenclature and State Variables
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We define the system state vector $\mathbf{x}(t)$ as:
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$$
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\mathbf{x}(t)=\big[s,\ v_1,\ v_2,\ T_c,\ T_s,\ p_A,\ p_T\big]^\top
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$$
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**Table 1: State Variables ($\mathbf{x}$)**
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| Category | Symbol | Description | Unit | Range |
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|:-------------- |:-------- |:-------------------------------- |:---- |:------------ |
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| **Electrical** | $s(t)$ | State of Charge (SOC) | 1 | $[0, 1]$ |
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| | $v_1(t)$ | Fast Polarization Voltage (RC-1) | V | $\mathbb{R}$ |
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| | $v_2(t)$ | Slow Polarization Voltage (RC-2) | V | $\mathbb{R}$ |
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| **Thermal** | $T_c(t)$ | Battery Core Temperature | K | $>0$ |
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| | $T_s(t)$ | Battery Surface Temperature | K | $>0$ |
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| **Network** | $p_A(t)$ | Probability of RF Active State | 1 | $[0, 1]$ |
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| | $p_T(t)$ | Probability of RF Tail State | 1 | $[0, 1]$ |
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**Table 2: Input and Algebraic Variables**
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| Category | Symbol | Description | Unit |
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|:------------------------------ |:-------------------- |:------------------------------ |:-------- |
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| **Inputs** $\mathbf{u}(t)$ | $b(t)$ | Screen Brightness (Normalized) | 1 |
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| | $u_{\text{cpu}}(t)$ | CPU Utilization | 1 |
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| | $f(t)$ | CPU Frequency | Hz |
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| | $S(t)$ | Signal Strength | dBm |
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| | $\lambda(t)$ | Session Arrival Rate | s$^{-1}$ |
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| | $T_{\text{amb}}(t)$ | Ambient Temperature | K |
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| **Algebraics** $\mathbf{y}(t)$ | $P_{\text{req}}(t)$ | Total Device Power Demand | W |
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| | $P_{\text{batt}}(t)$ | Battery-Side Power Load | W |
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| | $I(t)$ | Discharge Current | A |
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| | $V(t)$ | Terminal Voltage | V |
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---
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# 3. Subsystem 0: Device Power Demand & Network Tail States
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To ensure reproducibility, we decompose the total power demand $P_{\text{req}}(t)$ into component-level contributions:
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$$
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P_{\text{req}}(t) = P_{\text{base}} + P_{\text{disp}}(b) + P_{\text{cpu}}(u_{\text{cpu}}, f) + P_{\text{gps}}u_{\text{gps}} + P_{\text{net}}(p_A, p_T, S)
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$$
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## 3.1 Display Power ($P_{\text{disp}}$)
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Using an affine model for LCD backlight power:
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$$
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P_{\text{disp}}(b) =
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\begin{cases}
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0, & b=0 \\
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\alpha_{\text{bl}} + \beta_{\text{bl}} b(t), & b \in (0, 1]
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\end{cases}
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$$
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Parameters $(\alpha_{\text{bl}}, \beta_{\text{bl}})$ are fitted from minimum/maximum backlight measurements.
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## 3.2 CPU Power ($P_{\text{cpu}}$)
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To support DVFS (Dynamic Voltage and Frequency Scaling), we employ:
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$$
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P_{\text{cpu}}(t) = P_{\text{cpu,idle}} + u_{\text{cpu}}(t) \big( \alpha f(t)^\beta + \gamma \big)
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$$
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where parameters are derived from system power profiles (e.g., `power_profile.xml`).
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## 3.3 Network Power with Tail States ($P_{\text{net}}$)
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We model the Radio Resource Control (RRC) using a **CTMC**. Let $p_I = 1 - p_A - p_T$. Assuming Poisson arrivals with rate $\lambda(t)$ and exponential service times:
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**Kolmogorov Forward Equations:**
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$$
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\begin{aligned}
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\dot{p}_A &= \lambda(t) p_I - \frac{1}{\tau_{\text{tx}}} p_A \\
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\dot{p}_T &= \frac{1}{\tau_{\text{tx}}} p_A - \frac{1}{\tau_{\text{tail}}} p_T
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\end{aligned}
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$$
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The expected network power is the probability-weighted sum of state currents:
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$$
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P_{\text{net}}(t) = V_{\text{nom}} \Big( I_{\text{idle}}(S) + p_A I_{\text{act}}(S) + p_T I_{\text{tail}}(S) \Big)
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$$
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This explicitly captures the "energy tail" ($\tau_{\text{tail}}$) where the radio consumes high power waiting for subsequent packets.
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> **[Figure 2 Suggestion: RRC State Transition Diagram]**
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>
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> * **Content:** States (Idle, Active, Tail) with transition arrows labeled with rates ($\lambda, 1/\tau$).
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> * **Why:** Visualizes the "hidden" power drain mechanism.
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---
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# 4. Subsystem I: Electrical Dynamics (2RC ECM)
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## 4.1 SOC Dynamics (Coulomb Counting)
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The effective capacity is $Q_{\max} = 3600 \cdot Q_{\text{nom}} \cdot \text{SOH}_C$ (in As).
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$$
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\dot{s}(t) = -\frac{I(t)}{Q_{\max}}, \qquad s(0) = s_0 \in (0, 1]
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$$
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## 4.2 Polarization Dynamics
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The transient voltage response is governed by two RC pairs:
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$$
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\dot{v}_i(t) = -\frac{1}{R_i C_i} v_i(t) + \frac{1}{C_i} I(t), \qquad i=1, 2
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$$
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## 4.3 Terminal Voltage and Arrhenius Correction
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We define the "Virtual Voltage" $V_{\text{virt}}$ (voltage before ohmic drop):
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$$
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V_{\text{virt}}(t) = U_{\text{ocv}}(s(t)) - v_1(t) - v_2(t)
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$$
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The terminal voltage is:
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$$
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V(t) = V_{\text{virt}}(t) - R_0(T_c) I(t)
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$$
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Crucially, we incorporate the temperature dependence of internal resistance using the **Arrhenius equation**:
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$$
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R_0(T_c) = R_{0,\text{ref}} \exp\left( \frac{E_a}{k_B} \left( \frac{1}{T_c} - \frac{1}{T_{\text{ref}}} \right) \right) \cdot g_R(\text{SOH}_R)
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$$
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This equation links the electrical and thermal subsystems, modeling voltage sag in cold environments.
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---
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# 5. Subsystem II: Thermal Model (Bernardi + Two-Node)
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## 5.1 Internal Heat Generation ($\dot{Q}_{\text{gen}}$)
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Following the Bernardi energy balance, the total heat generation includes irreversible Joule heating and reversible entropic heat:
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$$
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\begin{aligned}
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\dot{Q}_{\text{irr}} &= I^2 R_0 + \frac{v_1^2}{R_1} + \frac{v_2^2}{R_2} \ge 0 \\
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\dot{Q}_{\text{gen}} &= \dot{Q}_{\text{irr}} - I T_c \xi(s), \qquad \text{where } \xi(s) = \left. \frac{\partial U_{\text{ocv}}}{\partial T} \right|_{T_{\text{ref}}}
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\end{aligned}
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$$
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## 5.2 Two-Node Heat Transfer
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We model the battery core ($c$) and surface ($s$) separately to capture thermal inertia:
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$$
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\begin{aligned}
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C_c \dot{T}_c &= \dot{Q}_{\text{gen}} - \frac{T_c - T_s}{R_{\text{int}}} \\
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C_s \dot{T}_s &= \underbrace{\kappa_{\text{dev}} P_{\text{req}}}_{\text{Device Heating}} + \frac{T_c - T_s}{R_{\text{int}}} - \frac{T_s - T_{\text{amb}}}{R_{\text{ext}}}
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\end{aligned}
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$$
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Here, $\kappa_{\text{dev}} P_{\text{req}}$ accounts for heat conducted from the phone's processor to the battery surface, a critical factor in modern compact devices.
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> **[Figure 3 Suggestion: Thermal Network Schematic]**
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>
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> * **Content:** Core node linked to Surface node linked to Ambient. Surface node receiving external heat flux $\kappa P_{req}$.
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> * **Why:** Illustrates the complete thermal environment.
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---
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# 6. Subsystem III: PMIC Closure and DAE Formulation
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## 6.1 Battery-Side Power Demand
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Considering the efficiency $\eta_{\text{pmic}}$ of the DC-DC converter:
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$$
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P_{\text{batt}}(t) = \frac{P_{\text{req}}(t)}{\eta_{\text{pmic}}}
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$$
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## 6.2 The Algebraic Constraint
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The PMIC imposes a Constant Power Load (CPL) constraint, forming the algebraic part of our DAE:
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$$
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\mathcal{G}(\mathbf{x}, I, t) = V(\mathbf{x}, I) \cdot I - P_{\text{batt}}(t) = 0
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$$
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Substituting $V = V_{\text{virt}} - I R_0$:
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$$
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R_0 I^2 - V_{\text{virt}} I + P_{\text{batt}} = 0
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$$
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## 6.3 Discriminant Analysis
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The quadratic discriminant determines the system's solvability:
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$$
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\Delta(t) = V_{\text{virt}}(t)^2 - 4 R_0(T_c) P_{\text{batt}}(t)
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$$
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The roots for current are:
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$$
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I_{\pm}(t) = \frac{V_{\text{virt}} \pm \sqrt{\Delta}}{2 R_0}
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$$
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---
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# 7. Theoretical Analysis: Stability and Bifurcation
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To satisfy the rigor required for an Outstanding paper, we provide proofs for solvability and stability.
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### Lemma 4.1 (Existence and Boundedness)
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For any locally bounded input $I(t)$, the linear subsystems (Polarization $\dot{v}_i$ and Thermal $\dot{T}$) possess unique, absolutely continuous solutions. By the comparison principle, $T_c, T_s > 0$ for all $t$.
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### Theorem 4.1 (Stability of Branch $I_-$)
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Consider the PMIC regulation dynamics with time constant $\tau_I$. The Jacobian of the system is $J = -\frac{1}{\tau_I} (V_{\text{virt}} - 2 R_0 I)$.
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* At $I_-$, $V_{\text{virt}} - 2 R_0 I_- = +\sqrt{\Delta} > 0 \implies J < 0$ (Stable).
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* At $I_+$, $V_{\text{virt}} - 2 R_0 I_+ = -\sqrt{\Delta} < 0 \implies J > 0$ (Unstable).
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**Conclusion:** The physical system naturally selects the **lower current branch** $I(t) = I_-(t)$.
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### Theorem 4.2 (Index-1 Property)
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If $\Delta > 0$, then $\frac{\partial G}{\partial I} = -\sqrt{\Delta} \neq 0$. By the Implicit Function Theorem, the DAE is of **Index-1** and possesses a unique local solution.
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### Theorem 4.3 (Voltage Collapse / Saddle-Node Bifurcation)
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The condition $\Delta(t) = 0$ represents the limit of power transfer. If $P_{\text{batt}} > \frac{V_{\text{virt}}^2}{4 R_0}$, then $\Delta < 0$ and no real solution exists. This corresponds to a **Voltage Collapse**, physically manifesting as a sudden device shutdown. This explains shutdowns under high load, low SOC, or cold temperatures (high $R_0$).
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> **[Figure 4 Suggestion: PV Curve Bifurcation]**
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>
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> * **Content:** Plot $P_{out} = VI$ vs $I$ (parabola). Horizontal line $P_{batt}$.
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> * **Annotations:** Mark stable root ($I_-$), unstable root ($I_+$), and the collapse point ($\Delta=0$).
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---
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# 8. Final Closed-Loop System
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The complete Multi-Physics Coupled ODE-DAE System is summarized below. This system is solved numerically to generate the Time-to-Empty predictions.
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### 8.1 ODE Dynamics
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$$
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\left\{
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\begin{aligned}
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\dot{s} &= -\frac{I}{Q_{\max}} \\
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\dot{v}_1 &= -\frac{1}{R_1 C_1} v_1 + \frac{1}{C_1} I \\
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\dot{v}_2 &= -\frac{1}{R_2 C_2} v_2 + \frac{1}{C_2} I \\[2mm]
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\dot{p}_A &= \lambda (1 - p_A - p_T) - \frac{1}{\tau_{\text{tx}}} p_A \\
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\dot{p}_T &= \frac{1}{\tau_{\text{tx}}} p_A - \frac{1}{\tau_{\text{tail}}} p_T \\[2mm]
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C_c \dot{T}_c &= \left( I^2 R_0 + \frac{v_1^2}{R_1} + \frac{v_2^2}{R_2} - I T_c \xi \right) - \frac{T_c - T_s}{R_{\text{int}}} \\
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C_s \dot{T}_s &= \kappa_{\text{dev}} P_{\text{req}} + \frac{T_c - T_s}{R_{\text{int}}} - \frac{T_s - T_{\text{amb}}}{R_{\text{ext}}}
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\end{aligned}
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\right.
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$$
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### 8.2 Algebraic Closure
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$$
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I(t) = \frac{V_{\text{virt}} - \sqrt{V_{\text{virt}}^2 - 4 R_0 P_{\text{batt}}}}{2 R_0}, \quad \text{where } P_{\text{batt}} = \frac{P_{\text{req}}}{\eta_{\text{pmic}}}
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$$
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### 8.3 Termination Events
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The simulation halts at $t_{\text{end}}$ when any of the following occur:
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1. **SOC Depletion:** $s(t) \le 0$
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2. **Under-Voltage Protection:** $V(t) \le V_{\text{cut}}$
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3. **Voltage Collapse:** $\Delta(t) < 0$
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